My goal was to investigate the effect of placing a 1k ohm resistor as the input of the DC port of the Bias Tee. The expectation was it would decrease the bandwidth around DC, and this is supported by LTspice simulation. According to simulation, at around 300 Hz there becomes a few dB difference between having the resistor and not having it. From the paper 'W. Zhang, M. J. Martin, C. Benko, J. L. Hall, J. Ye, C. Hagemann, T. Legero, U. Sterr, F. Riehle, G. D. Cole, and M. Aspelmeyer, "Reduction of residual amplitude modulation to 1 × 10-6 for frequency modulation and laser stabilization," Opt. Lett. 39, 1980-1983 (2014)'(https://www.osapublishing.org/ol/abstract.cfm?URI=ol-39-7-1980) in Figure 2B we see the frequency noise without servos active. The noise falls off after around 50 Hz, which indicates the change of bandwidth to 300 Hz should not be an issue. I also showed the effect for 500 ohms to see how the transfer function changes intermediately between 0 and 1k ohm resistances.
Also, I found that the effective reflectivities from the top surface of layers calculated in Evans et a. PRD 78, 102003 (2008) were different from reflectivities calculated by matrix method in Hong et al. PRD 87, 082001 (2013). It turned out that the sign before phase in Eq. B3 and B4 in Evans et a. PRD 78, 102003 (2008) were opposite to what comes from the matrix method. After discussions with Gabriele, I came to the conclusion that this sign only creates a difference of giving complex conjugates of effective reflectivity. But to have consistency, I have corrected the sign of phase in the new code. Attached is a comparison of old effective reflectivity and the new one. One can see that the imaginary values are opposite in sign but everything else matches perfectly. Also, this has no effect on the effective coating coefficient of thermo-refraction.
Today I ran the two codes with the same parameter values to check if the effective reflectivities calculated during the calculation of thermo-optic nose matches. They do match exactly actually. Attached is an over plot.
Coating effective coefficient of thermo-refractive effect comes out to be:
Old Code: 8.61(46)e-05 K**-1
New Code: (8.59+/-0.21) e-05 K**-1
So this discrepancy was not really there. I was just comparing apples with oranges earlier.
The effective coating CTR in the previous code was 7.9e-5 1/K and in the new code, it is 8.2e-5 1/K. Since this value is calculated after a lot of steps, it might be round off error as initial values are slightly off. I need to check this calculation as well to make sure everything is right. Problem is that it is hard to understand how it is done in the previous code as it used matrices for doing complex value calculations. In new code, I just used ucomplex class and followed the paper's calculations. I need more time to look into this too. Suggestions are welcome.
Following points are in relation to previously used noisebudget.ipynb file.
Following points are in relation to the new code at https://git.ligo.org/cit-ctnlab/ctn_noisebudget/tree/master/noisebudget/ObjectOriented.
The new noise budget code is ready. However, there are few discrepancies which still need to be sorted.
The code could be found at https://git.ligo.org/cit-ctnlab/ctn_noisebudget/tree/master/noisebudget/ObjectOriented
Please look into How_to_use_noiseBudget_module.ipynb for a detailed description of all calculations and code structure and how to use this code.
In the previous code, while doing calculations for Thermoelastic contribution to Photothermal noise, the code used a weighted average of coefficients of thermal expansion (CTE) of each layer weighted by their thickness. However, in the same code, while doing calculations for thermoelastic contribution to coating thermo-optic noise, the effective CTE of the coating is calculated using Evans et al. Eq. (A1) and Eq. (A2). These two values actually differ by about a factor of 4.
Currently, I have used the same effective CTE for coating (the one from Evans et al) and hence in new code, prediction of photothermal noise is higher. Every other parameter in the calculations matches between old and new code. But there is a problem with this too. The coating thermoelastic and coating thermorefractive contributions to photothermal noise are no more canceling each other out as was happening before.
So either there is an explanation to previous codes choice of using different effective CTE for coating, or something else is wrong in my code. I need more time to look into this. Suggestions are welcome.
With comparison with old estimates:
I measured dark noise of the beatnote detector reaching moku and its effect on measured beatnote frequency noise.
Today, I added a new out-of-loop transmission PD (Thorlabs PDA10CS) for the south path. This will be helpful in future measurements of RIN coupling to beatnote noise. This PD is added at (1, 40) using the dumped light. The optical layout would be updated in a few days. I've confirmed that this photodiode is reading the same RIN as read earlier in CTN:2555. I've also connected Acromag channel for South Transmission DC to this photodiode, so the transmitted power channels and the mode matching percentage channel of South Cavity are meaningful again.
Today, I added a new out-of-loop transmission PD (Thorlabs PDA10CS) for the north path. This will be helpful in future measurements of RIN coupling to beatnote noise. This PD is added at (8, 42) using the dumped light. The optical layout would be updated in a few days. I've also connected Acromag channel for North Transmission DC to this photodiode, so the transmitted power channels and the mode matching percentage channel of North Cavity are meaningful again.
ISS Gain for the Northside has been increased to 2x10000 since half of the light is now being used by the OOL PD.
I was finding myself changing thresholds every time I change power levels. Also, the fastmon rms monitors were not working with the docker-compose. I'm listing all script and medm changes since the sad departure of awade:
I'm attaching screenshots of modified medm screens.
Last night I soldered together four BNCs and attached them to one of the acromags with some free channels. Turns out this acromag is named vader (10.0.1.50), and was being used for temperature sensors.
I just added all four channels into /home/controls/modbus/db/LaserSlowControlsAndMonitors.db , and named the first two additions C3:PSL-SCAV_REFL_DC and C3:PSL-NCAV_REFL_DC
All of this was done so I could tell if the "breathing" we see in the TRANS_DC is really representative of power in the cavities or just some crap happening on our tiny ISS board in transmission. Seems like it's real power in the cavity, but we'll see after like an hour.
If so, we need to control the temperature of our EAOMs. Thermal hats, peltiers, I don't care, needs to happen ASAP.
Edit Thu Apr 12 22:09:21 2018 (awade): WRONG, THE ISSSUE IS THAT ACROMAG NEED MIN 6V TO OPERATE BINARY INPUTS
When Craig restarted the acromag IOC yesterday the North path FSS loop engage binary channel went into a permanent latch off mode. This is a recurring problem that can be fixed by plugging the 5 V power in line to the acromag binary channels in with the FSS control boxes unplugged. Sometimes you need to plug and unplug a few times.
It could be an issue with the way we have used 820 Ω resistors to bring the pull up 10 kΩ down to 758 Ω. It probably should be buffered somehow. For now its good enough to get it working, once it's powered up its fine.
As an intermediate fix I soldered a 1000 µF electrolitic cap in line with the 5V supply to give it juice when first powered up. This seems to make the latching go away most of the time (90%) when first powering up the units. So... slight improment.
Today I installed the Faraday isolator after the PMC. Tara and I then spent some time trying to figure out why the PDH error signal suddenly had a huge DC offset (it was because I accidentally knocked the angle control on one of the HWP mounts while installing the FI beam dump). Before installing the FI, we had observed that the loop oscillates noticeably at about 100 kHz and had hoped it was caused by back-reflection into the laser (which the FI would fix). Installing the FI seems to have no effect on the oscillations. After installing the FI I adjusted the HWP immediately following and retuned the phasing of the PDH loop by adding some extra cable to the PD SMA input. I've attached a picture showing the sweeps of the cavity refl response and PDH error signal, and a picture showing the oscillations when the loop is engaged.
I tried minimizing the rejected light out of the FI to optimize the angle of the QWP directly in front of the cavity, but this light appears to be dominated by reflections other than those off of the cavity. The rejected light consists of two distinct spots which can be seen with an IR card. I think one of them is a reflection from the lens immediately following the FI, and the other is a reflection from the 14.75 MHz EOM.
The computer acromag2 has inexplicably died. It turns up some error messages recovering jornal on /dev/sda1 that doesn't bode well. All computers in the lab are backed up to somewhere remote so nothing is lost. Also we version control everthing that matters on the computers anyway.
Rather than debugging a potentially faulty hard drive issue we will just replace the HD with one from the draw (Larry gave me a box of small/midsized hard drives about a month ago).
I showed Andrew how to set up the slow controls. We got the previous 3 ADC channels back up.
Measured the acromag noise (input and output).
For the input noise, a function generator was set up to input a sin signal of 0.1Vpp at 0.1Hz and connected to an input channel. The time series was recorded for 4 hours (sampled at around 10Hz, but not exactly due to differences in how long each loop took to run), and then the Lomb-Scargle algorithm (Fourier transform with uneven sampling) was applied to obtain a frequency spectrum. The result was then run through Andrew's rms.m script (attached). Both are plotted below:
For the output noise, a script was written to continuously write a 0.1Vpp at 0.1Hz sin signal to an output channel that was connected to the signal analyzer, which was used to take the following data.
I was double checking the UGF of the PLL and was getting the strange results of 8 kHz UGF with the standard settings of 10 kHz/V and SR560 set to 23 dB gain (Marconi was set to +13 dBm RF power level). In the past we got 30 kHz for this configuration.
Since then an acromag channel was connected to the same 600 Ω output of the SR560 as the Marconi signal generator. This was to monitor the state of the PLL loop so that the Marconi center frequency could be adjusted (through GPIB and a python script) to always have the PLL locked.
It turns out that the acromag channel monitoring the BN DC level is overloading/lowpass filtering the 600 Ω input. Attached below is a transfer function of the SR560 with 2x100 gain setting (no filtering): here the BN has been disconnected this is just the preamp itself. With the acromag connected it appears to add a pole at 3 kHz. This will have changed the PLL loop response in recent measurments.
I have now moved the acromag to the 50 Ω buffered output of the SR560, reported voltages should be the same (acromag is high impedance) but the loop now has the expected 30 kHz as before. Calibrations of previous week should be taken with a grain of salt.
I had hooked up the a channel to monitor the tank temperature. However, now I am seeing random noise and also zero readouts on every other sample.
I had something similar over the last week when I was trying to set up autolocker and PID slow controls for the laser. The fast monitor signal reported by epics was very noise. There I thought it was just poor performance of the FSS locking loops and that I would need to get in and check alignments, polarisations etc. Now I'm thinking there is something wrong with the chain from the ADC to what caget spits out.
A calibrated voltage input of +2 V was put into the C3:PSL-VACTEMP_MON1 channel (acromag channel regiser 7 (out of 0-7). A quick grab of the ouput is attached below, it doesn't look great. Might have to look tomorrow to see if this is something to do with modbus dropping measurments or if there is some other issue.
I managed to figure out the modbusDrv configuration settings to get the binary output of the Acromag working. I've updated the Wiki page to reflect this. I've wired the XT1541 DAC, BIO Acromag unit to the T1EN and T2EN channels on the TTFSS box but I still can't get remote control of it yet for some reason. When the PDH loop is closed and I switch the TTFSS box to REMOTE, the loop stays closed regardless of what I do to the binary outputs in EPICS.
I configured the Acromag XT1541 DAC to run with EPICS. This was a touch trickier than the ADC as there is a subtlety with the channel configuration in the EPICS database. The bottom line is that now I can change the value in an EPICS channel and a multimeter attached to the unit will show a corresponding change in voltage.
The attached files (ioctest2.cmd and IOCTEST2.db) are used to access the first output channel, OUT00, on the unit. Now that I've got the thing working I can debug the calibration. Once that's sorted I'll summarize the set-up procedure on a Wiki page with glorious detail for future reference.
The following command line is used to open the modbus EPICS server.
The ioctest1 files are for the ADC unit.
field(OUT, "@asynMask(DAC_Reg, 0, -16)MODBUS_DATA")
field(SCAN, ".1 second")
field(INP, "@asynMask(ADC_Reg 0 -16)MODBUS_DATA")
field(SCAN, ".1 second")
I set up an Acromag slow controls based on the procedure that Keith wrote in T1400200. It's really pretty easy. It took an hour and 15 minutes from installing Ubuntu on a machine to having a functioning ADC channel from the Acromag unit. I haven't yet set up a DAC unit - this will require some tweaking of some of the EPICS parameters. Once I've done that I'll upload a complete procedure to the Wiki.
This is relatively promising for supporting/replacing VME slow channels.
found the old data from the seismometer measurements we did some time ago. Measurements agree more or less. Seismic noise floor measured some time ago was higher above 30Hz, but that was measured at the time where we had the construction going on and not during vacation time.
Measured the noise floor of the accelerometer to compare it with the seismic noise we measure with it (and the TFs i want to measure). Suspended it from the table using a very soft spring to make it quiet enough. Resonance frequency of suspension was ~1Hz (small peak visible in spectrum, damping of the thing took forever).
Seismic noise of the table is hitting the noise floor of the accelerometer at about 10Hz. Couldn't find the raw data from the seismometer measurements. Will update this later.
[Rana, Tara, Evan, Eric, Nic]
We are designing a PMC, to do that we should be able to answer some fundamental questions about a PMC.
Why do we want a PMC?
What should we consider in the design of the cavity?
What should we consider in the design of the spacer?
Considerations for PMC design:
RXA: In general, all of these considerations need some sort of quantitative detail. Make a DeBra Matrix so that we can evaluate.
There appears to be a factor of 5/3 difference between the ASD output of the SR785 and the CRIME lab's cymac3 ADC. To be clear, . I am not sure why at this point.
Earlier today, Gabriele helped me calibrate cymac3, telling me the voltage range (+- 10V) and ADC bit number (16, so 2^16 = 65k counts), giving a calibration of . When I apply this calibration to the median-averaging ASD code Gautam provided me, I appear to underestimate the true ASD, where the "true ASD" is as reported by my SR785.
The first plot is the SR785's response to a 1 Vrms sine wave at 512 Hz, with 1 Hz bin widths. The ASD peak at 512 Hz reaches 0.7086 Vrms/rtHz.
The second plot is the calibrated cymac3 ADC response with 1 Hz bin widths. At 512 Hz it reaches only 0.4252 Vrms/rtHz.
In the end, I decided to just apply the mystery gain of 5/3 to the ADC. This is the final plot. Seems close enough.
This ratio of 5/3 is suspicious and makes me think the calibration of the ADC is wrong. I am having trouble locating the ADC datasheet. I checked around at a couple of injection frequencies and things seem consistent with the correction factor applied. I will look more into the ADC in the morning, but I don't want to spend very much more time on this. The whole point is to have a quick, constant check on our beatnote ASD which is continually being saved and compared to the ASD from five minutes ago, ten minutes ago, an hour, a day, to easily see how our final product, the beatnote ASD, is moving all the time. If we kill a bunch of noise, we want to know when and why.
EDIT: I checked the time series signal and found that the ADC was reporting half of what I was putting in. This is because the cymac3 is expecting differential inputs, and our beatnote BNC is grounding the low input. I didn't understand differential and single-sided ADCs until today, after reading this. Turns out the fully-differential is able to double its input range sensitivity with the same voltage range input by splitting the input 50/50 and flipping the low input's phase by 180 degrees. If you ground the low input, you halve your signal. I corrected for this by multiplying my calibration by a factor of two to account for my signal being halved.
So now my factor of 5/3 becomes a factor of 5/6.
But the problem still remains, why is the median-averaged ASD from the ADC and RMS ASD from my SR786 for my 1 Vrms sine wave injection giving different final results?
To explain this correctly, I have to go through the median ASD estimation process in Gautam's python code.
First, we use scipy.signal.spectrogram to estimate a bunch of PSDs from our input time series. We take the square root to get ASDs. Then, we collapse along the time dimension by taking the median value for each frequency bin, call this the median ASD. Finally, we divide by the bias factor of to get from a median ASD to an RMS ASD, the industry standard. This shown in Evan's thesis, Appendix B.
However, I misunderstood some of Evan's assumptions in this thesis. Importantly, the Rayleigh distribution for magnitude is only good for zero-mean Gaussian noise. If you inject a signal, your mean and your median are gonna be about the same at that frequency, because the signal completely drowns out the noise. You have to first eliminate your signal, apply the bias to go from a median to RMS ASD, then add the signal back in.
If you ignorantly multiply your entire ASD, including signal, by , like I did, you will find that your ADC calibration results seem to be overestimated by a factor of about 5/6, because .
To test this, Gautam and I used the RIGOL function generator to generate 1 Vrms of noise. We found that (1) the two channels of the RIGOL produce very different actual levels of noise when 1 Vrms is requested, and (2) our median-averaged ASD python code produced the same noise levels as the RMS ASD taken by diaggui, which we are sure is right.
This is encouraging. We now trust that the median averaged ASD estimation code is doing the right thing, particularly since it matches up with diaggui's output. But the python code has the advantage of (1) being in python, (2) being median-averaged, and therefore robust to glitches, which our PLL has every time we change the Marconi carrier frequency, and (3) being easily callable and controllable whenever we want to take a permanent spectra.
I won't save every plot we make permanently, because each plot is ~200K, and there are 1440 minutes in a day, so 288M in plots would quickly become ridiculous. But I think saving one from every thirty minutes is good, ~1M of plots each day is doable.
seems like a bad AOM and an impedance matching problem together. exchanging the semi-rigid cable by other cables produces a lot of different results in power modulation / pointing vs frequency. right now i found a combination where for frequencies 80MHz and higher it is almost flat, but below it drops a lot. the pointing is related to the absorbed power in the AOM. - you can really feel the heat of the crystal, no joke. will measure the temp on tomorrow for different frequencies where the pointing is worst case to see if it is a macroscopic change in temp. Aidan has this nice thermal image camera to do this. i think we should try the crystal technology AOM we have. i don't think that aligning helps a lot here. tried this the whole afternoon :-( the lowest power modulation over the entire frequency range is about 20%pp
New setup for fiber phase noise cancellation with one AOM
I made drawings for aom block and adaptor plate. The assembly is for 3" beam height.
The assembly is consisted of two parts. The bottom aluminum part is for mounting new focus 9071 4 axis stage on the table.
The top plastic part, is for mounting an AOM to the 4-axis stage.
The bottom part actually is designed for a standard EOM, so the height is 3". With a plastic adaptor plate, it can be used for an AOM as well, so I'll order a few of the alumnium parts.
There are 2 designs for AOM adaptor parts, because we have two AOM models. They have different screw size and mounting positions, I 'll order a couple for each design.
As Frank suggested, I edited the drawing, so that the adaptor plate can accommodate both types of AOM.
I made a simulation for PMC body mode, and found out that for Al PMC, the first body mode is 1kHz. And 780 Hz for stainless steel pmc.
November 27, 2012
It is desirable for the first body mode of the PMC to be at or above 1000 Hz in order to provide consistent length for the cavity.
Above you can see the first mode shape of the PMC. The colors represent the displacement - deep blue indicates no motion, while red indicates the greatest amount of motion. The animation of this mode shape shows the PMC spacer rocking transversely on the PMC base. The PMC base does not move at all.
One question that came up is whether ANSYS is importing the geometry file at the correct size. According to the scale on the screen, it is the right size. However, when the material is changed to resemble fused silica, the lowest body mode is 998 Hz, which is about an order of magnitude lower than expected. This indicates some other error, possibly in importing the structure into ANSYS.
/more to come
Above you can see the first mode shape of the PMC. The colors represent the displacement - deep blue indicates no motion, while red indicates the gr
This does not look like a longitudinal mode. Do you have the frequency for the first longitudinal mode(along cavity length)? the first longitudinal mode should look like this ( this model has no fixed boundary condition, just a block in space).
Kristen and Norna came to ATF for impact-hammering of the metal PMC in the gyro setup
The AEOM has been installed in the South path replacing the EOM 21MHz used for the PMC. There is a high noise that I clearly see at the photodiode in transmission.
When I have placed the AEOM in the path I have decided to take the alignment of the previous EOM as reference. Not ideal because the reference should be the incoming beam. The beam is not parallel to the table and it was decided to be as less as possible invasive. The mode matching and the alignment gave at that time 20% of visibility (at each polarization). After the installation parameters where unchanged. Later I have improved the alignment bringing the visibility at 30% for both the polarizations. After that, when everything was in place I have easily locked the cavity but the power in transmition was showing a very high noise. I have spent all the day trying to twick the alignment because and servo loop gain, but we need to solve this before going further. My back does not allow me to proceed for today.
I have also noted that the South Laser which is labeed 2W laser has the lambda/4 and the lambda/2 rotated in a way that at the output of FI we had few mm. I am not sure if damping the power at the FI is a good thing.
in order to gain more s/n ratio i modified the existing AD590 readout-box a little bit. I assumed that we wanna operate the cavity at 35C (which is not too high but well above RT or the temp of an additional temp stabilized box around both cavities) The required range for shifting the cavities is ~ 1 FSR, better would be a little bit more for each cavity as we can shift both independent.
df~156MHz /K and 1 FSR~740MHz
this corresponds to ~4.75K/FSR we have to shift.
For testing purposes it might be helpful to have more than that as e.g. if we limit the total range to lets say 6K we might end up at the end of the range and run into trouble as soon some disturbance from outside (e.g we remove part of the insulation, lets say an end cap) might shift the whole thing at the end of the range. As soon as this happens the servo would go crazy.
So i think we should go for 10K range, centered around 35C, so from 30C to 40C. I modified the box for that, so the transimpedance resistors have now a value of 29.4K, which gives us ~9.21V for 40C at the output of this stage.
In order to supply it from an independed power supply to reduce our current ground loops, i've chosen a WM071, the same as we use for the PDH boxes. As they come only in +/-15V, i had to change the voltage regulators in the box to +/-12V instead of =/-15V.
This results in a maximum output voltage of the LT1125 of a couple of 100mV more than 10V, depending on the current they have to source/sink. So 9.2V is still well below the max.
I added a filtered 5V reference, (AD586, 4.7uF filter cap) for the dc offset @35C. The corresponding resistor for the summing amp is 1379.76 which can be implemented almost exact using 2k05 and 4k22 in parallel (1379.7) or 1k54 and 13k3 (1380.2). The feedback resistor of the last stage can then be calculated to be 170k45 in order to match 30C to 40C to -10V to 10V. Paralleling can be used here as well to get an almost exact value.
The matching is not that critical as we don't wanna measure absolut temp, but if can do it that easy why not.
--- new schematic following soon ---
Because of the previous data comparing the open box vs the closed box was varying unexpectedly, I re-ran the experiment with both sets of data taken on the same day.
Now both sets of data show very similar curves, with the box open data slightly above the closed data in most areas. Maybe the last data was different due to other systematic conditions on that day, but it does seem like now the difference is gone. Both sets follow the original closed box data measurement from before.
I reflow soldered 3 channels to an AD590 temperature board for a differential measurement test. I expect to run the experiment soon to see the noise of the sensor.
show us what you got for the LISO or ZERO noise budget of this circuit before testing; also sketch of the experiment setup
ACAV's PD for transmitted beam is connected to PSL1
RCAV's PD for transmitted beam is connected to PSL2
And now RCAV_RCTRANSPD dropped from ~5.3 to ~5.05
ACAV_RCTRANSPD dropped from ~2.5 to ~2.4
We swept the temperature of the ACAV laser and monitored the transmission through the cavity. In the attached image, the TEM00 modes (separated by 3GHz or 1 FSR) are located at C3:PSL-ACAV_SLOWOUT values of 0.5344V and 1.379V. There is a TEM20 mode at 1.52V.
current heater value is around 4.66. changed crate startup value to current value
re-aligned the ACAV once more, now about 91% are coupled into the cavity
I put most optics on ACAV path. I have not tried to lock the cavity yet. I'll install ACAV RFPD next.
summary of all changes made and more detailed plots will be posted soon, so check back later
writing in progress
ACAV loop is now completely free from line harmonics and the in-loop level dropped to ~10nV/rtHz (includes 7nV/rtHz from analyzer). Mixer dark noise is ~25nV/rtHz.
I updated the schematic for ACAV RFPD.
I'll update the schematic for RCAV servo, ACAV servo as well.
The ACAV RFPD stopped working this afternoon. It had high current consumption on the +15V supply, causing the supply to drop down to 2.3V.
I turned out that the logic IC (U8, see schematic) was broken and so the +5V (internally regulated) caused the high current flow which is supplied from the +15V.
I removed U8 entirely as we don't need it. Pin7 of U2 can be left open according to the datasheet in order to enable the device. Diode is now working again.
Already yesterday we made several changes in order to make the RFPDs for both cavities the same. Basically more DC and AC gain.
Attached the modified schematic (only page 1) for ACAV RFPD. Changes are in red.
PID process running on the Sun workstation stopped at lunch time with error "couldn't read process variable ...bla bla bla "
Turned it on again.